Time-Multiplexed-Capacitor DC/DC Converter With Multiple Outputs

ABSTRACT

A multiple output DC-to-DC voltage converter using a new time-multiplexed-capacitor converter algorithm and related circuit topologies is herein disclosed. One embodiment of this invention includes a flying capacitor, a first output node, a second output node, and a switching network. The switching network configured to provide the following modes of circuit operation: 1) a first mode where the positive electrode of the flying capacitor is connected to an input voltage and the negative electrode of the flying capacitor is connected to ground; 2) a second mode where the negative electrode of the flying capacitor is connected to the input voltage and the positive electrode of the flying capacitor is connected to the first output node; and 3) a third mode where the positive electrode of the flying capacitor is connected to ground and the negative electrode of the flying capacitor is connected to the second output node.

BACKGROUND OF THE INVENTION

Three approaches are commonly employed in implementing DC-to-DCconverters—electronic circuits that converts a battery or DC voltagesource to a different DC voltage. These methods comprise linearregulation, inductive switching regulators or so-called “switch-modepower supplies,” and switched capacitor converters, also known as chargepumps. Of these methods, the charge pump is valued for its simplicity,cost effectiveness, and relatively low noise operation. Under certaincircumstances, the charge pump can operate at high conversionefficiencies, but not over the wide range of conditions that switchedinductor based converters can achieve.

The operating principle of a charge pump is straight forward comprisinga charging phase and a charge transfer phase which operate inalternating sequence. As shown in FIG. 1A, prior art charge pump doublertype circuit 1 comprises four MOSFETs, a flying capacitor not attachedpermanently to any specific supply voltage, and a grounded output filtercapacitor. In the charging phase, battery-connected MOSFET 3 andgrounded MOSFET 2 are turned on and allow conduct current and chargecapacitor 5, electrically connecting the capacitor in parallel with thebattery or voltage input to the circuit. MOSFETs 1 and 4 remain offduring the charging phase of operation. This charging current isindicated in the schematic 1 by a dashed line and arrow. After sometime, capacitor 5 charges to a voltage equal to the battery voltageV_(batt) and the charging current subsides.

During the charge transfer phase, capacitor 5 is connected in serieswith the battery, specifically with its negative terminal shorted to thepositive terminal of the battery achieved by turning on MOSFET 1. Thevoltage of the series combination of capacitor 5 stacked atop thebattery input has a voltage of V_(batt)+V_(batt)=2V_(batt), or twice thebattery voltage, hence the name “doubler” ascribed to this charge pump.This series circuit is simultaneously connected to output capacitor 6 byturning on MOSFET 4. Capacitor 5 then transfers its charge to outputcapacitor 6 until V_(out)→2V_(batt) as shown by the solid line andarrows.

After the initial charging of output capacitor 6, the charge pump'soperation becomes efficient since the only current flowing is thatneeded to replenish the charge lost on output capacitor 6 supplied tothe load. As long as the desired output voltage is twice that batteryvoltage, i.e. 2V_(batt), the efficiency of doubler charge pump 1 ishigh, even up to 98%. Any deviation between the actual output voltageV_(out) and the charge pump's ideal output V_(CP)=n·V_(in) will resultin a loss of efficiency as given by the relation

$\eta = {\frac{V_{out}}{V_{CP}} = \frac{V_{out}}{n \cdot V_{in}}}$

The voltage differential between the charge pump lowers efficiency bycausing one of the transistors to saturate a drop the incrementalbusiness. One common condition leading to lower efficiency in a doublercharge pump is “over-pumping” the output to a voltage higher thandesired or required by the load.

Fractional Charge Pump Implementation: A common solution is toover-pumping is to employ a fractional charge pump, one that steps up by1.5× rather than doubling its input. Such a fractional charge pump 20 asshown in FIG. 1B requires two flying capacitors 30 and 32, controlled bya matrix of MOSFET switches 21 through 27. Operation involves chargingseries-connected capacitors 30 and 31 through MOSFETs 21, 22 and 23 asillustrated by a solid line and arrow. After charging, the flyingcapacitors transfer charge from output capacitor 32 through conductingMOSFETs 24, 25, 26 and 27.

During charging, capacitors 30 and 31 are connected in series and chargeto a voltage equal to V_(batt)/2. During charge transfer, capacitors 30and 31 are wired in parallel, connected in series with the battery inputV_(batt) with the series combination connected across output capacitor32. The output voltage is charged to a voltage V_(out)→1.5V_(batt), avoltage 25% lower than the output of the doubler charge pump 1.

By employing a 1.5×-type fractional charge pump technique, efficiency isimproved at lower output voltages but limited to a maximum of 1.5 timesits input. Moreover, a 1.5× fractional charge pump, like the 2×-typecharge pump, does not regulate voltage. As a result, its output voltagevaries with its input which is undesirable in many applications.

Charge Pump Efficiency Considerations: Since a charge pump's outputvoltage varies with its input, it is not well adapted as a powerconverter and must often be combined with a linear regulator connectedin series with the charge pump, to limit the output voltage swing. Thelinear regulator may be connected in either the input or output of thecharge pump.

For example, a lithium ion input ranges from 4.2V to 3.0V during itsdischarge. Under such circumstances the output of a fractional 1.5×charge pump will vary in its output from 6.3V to 4.5V. A 2×-type chargepump doubler's output will vary from 8.4V to 6V under the samecircumstances. If the load voltage is maintained at a fixed voltage,either by a linear regulator or because the load clamps the voltageacross its terminals, then the efficiency will vary with the inputvoltage. The efficiency variation of linear regulated 1.5× and 2× chargepumps are summarized in the following table for a few commonly neededsupply voltages. The output voltages of unregulated charge pumps areincluded in the table for reference along with a linear regulator withno charge pump, referred to in the table as a 1× converter.

Unregulated Charge Voltage V_(CP) Lilon Regulation Efficiency η_(max) byV_(out) Pump Max Typ Min 1.8 V 2.5 V 3 V 3.3 V 5 V 2X 8.4 V 7.2 V 6 V21%-30% 30%-42% 36%-50% 39%-55% 60%-83% 1.5X 6.3 V 5.4 V 4.5 V   29%-40%40%-45% 48%-67% 52%-73% 80%-NA 1X 4.2 V 3.6 V 3 V 43%-60% 60%-83% 71%-NA79%-NA NA

As shown, each output voltage exhibits a range of efficiencies thatvaries with the battery's voltage, starting with a lower efficiency whenthe Lilon cell is fully charged to 4.2V and improving as the batterydischarges down to 3V. The term “NA” means not available, meaning thatthe charge pump is incapable of producing the desired output voltageover the full range of inputs. Efficiency has no meaning if the outputfalls out of regulation. It should be also be noted that the efficiencyshown in the table, given by the relation:

$\eta = {\frac{V_{out}}{V_{CP}} = \frac{V_{out}}{n \cdot V_{in}}}$

is the maximum theoretical efficiency of the charge pump, not takinginto account losses in MOSFET resistance, switching losses, or otherparasitic effects. The losses may further degrade efficiency by 3% to 6%below the theoretical maximum efficiency values shown.

From the table it is clear that efficiency is highest when the desiredoutput voltage is close to the unregulated charge pump voltage, i.e.when V_(out)≈V_(CP). Lower output voltages therefore suffer from lowerefficiencies because the charge pump is over-pumping the voltage to toohigh a value. For example a 1.8V volt output for a charge pump doublerhas a peak theoretical efficiency of 30% while a 3V output has aconversion efficiency of 50%. Under the same circumstances, thefractional charge pump has a higher efficiency, 40% for a 1.8V outputand 67% for a 3V output, because it is not pumping its output to as higha voltage as the doubler.

On the other hand, a fractional charge pump cannot output all thevoltages commonly desired in a system. For example, a 1.5× charge pumpcannot produce a 5V output over the full lithium ion range. At slightlyabove 3.3V the output voltage will sag below the desired 5V and thesystem may fail, meaning a 1.5× charge pump cannot be used reliably toproduce a 5V regulated supply, despite having a higher efficiency whenit is able to do so.

So if higher charge-pump multiples are used, e.g. n=2, the converterregulates over a wider voltage range but operates at lower efficiencies.If lower conversion factors of n are used, e.g. n=1.5 or even n=1, thenthe converter cannot supply the voltage over the full battery operatingrange unless the condition V_(CP)(min)>V_(out) can be maintained.

One solution to the range versus efficiency tradeoff is to employ modeswitching, i.e. to combine the doubler and fractional charge pumps intoa single circuit, operating in 1.5× mode until the battery dischargesand switching into 2× mode when the battery discharges. In this manner ahigher average efficiency may be maintained over the battery voltagerange. Such mode switching charge pumps capable of operating at twodifferent values of “n”, in this case at 1.5× and 2×, are referred to asdual-mode charge pumps.

For outputs such as 3V and 3.3V even the 1× mode, or linear regulatoronly mode, may be used for some portion of time before the charge pumpneeds to turn on. By combining 1.5× and 1× mode charge pumps into asingle charge pump, the resulting dual-mode charge pump is betteradapted to lower voltage outputs than combining 2× and 1.5× modes.

Even more versatile, but slightly more complex a tri-mode charge pump,may operate in any of three modes, for example operating instep-down-only 1×-mode when the battery is charged, switching to 1.5×mode as the battery becomes discharged, and jumping into 2× mode if ahigher voltage or current is temporarily demanded by the load. As oneexample, a tri-mode charge pump can drive 3.6V white LEDs as the backlight in a cell phone using its 1.5× and 1× modes, and then momentarilyswitch into 2× mode whenever the 4.5V camera flash LEDs are needed.

An example of a tri-mode charge pump 35 is illustrated in FIG. 1C wherethe charging and discharging of flying capacitors 45 and 46 arecontrolled by a matrix of MOSFET switches. This matrix combinestopological elements of charge pump doubler circuit 1 with fractionalcharge pump 20, along with the means by which the entire charge pumpcircuit may be bypassed to achieve 1× pass-through operation.

Except in 1× bypass mode where the charge pump is not switching,tri-mode charge pump 35 operates by the same principal as single-modecharge pumps 1 and 20, i.e. by successively charging flying capacitors45 and 46 to a voltage V_(fly), then transferring their charge to outputfilter capacitor 49 as needed. In the 1.5× mode, the capacitors areseries connected and each charged to a voltage of V_(batt)/2 throughconducting MOSFETs 36, 37 and 38 while all other MOSFETs remain off. In2×-mode, each flying capacitor is placed in parallel with the batteryand charged to a voltage V_(batt) through conducting switches 36, 39, 42and 38 while all other MOSFETs, including MOSFET 37 remain off.

The charge transfer mode is the same regardless whether flyingcapacitors 45 and 46 are charged to a voltage V_(batt) or V_(batt)/2.Conducting MOSFETs 40 and 42 connect the negative terminals of chargedcapacitors 45 and 46 to the input voltage V_(batt). Conducting MOSFETs43 and 44 along with forward biased diodes 47 and 48 connect thepositive terminals of charged capacitors 45 and 46 to the converter'soutput and to filter capacitor 49. Charge transfer there occurs so thatV_(out)→(V_(batt)+V_(fly)). If V_(fly) is charged to a voltage V_(batt),then V_(out)→2V_(batt) and charge pump circuit 35 operates as a doubler.If V_(fly) is charged to a voltage V_(batt)/2, then V_(out)→1.5V_(batt)and circuit 35 operates as a 1.5×-type fractional charge pump.

To operate in 1× bypass mode, conducting MOSFETs 36, 42, 43, 44 andoptionally 40 and 37 connect V_(out) directly to V_(batt). No switchingaction is needed in this operating mode.

So aside from the disadvantage of containing a large number of MOSFETsto implement the switching matrix, tri-mode charge pump 35 can adjustits mode to reduce over-pumping and improve operating efficiency at anygiven output voltage.

Limitations of Charge Pumps: Many systems today require more than oneregulated output voltage. One solution to this problem is to step up thebattery voltage with a charge pump and then regulate down to lowervoltages using more than linear regulator as illustrated in schematic 50of FIG. 2.

As shown charge pump 51 powered by Lilon battery 58 generates a voltageV_(CP) which is stored on reservoir capacitor 57 and then regulated bylinear regulators 51, 52, and 53 to produce various required regulatedvoltages V_(out1), V_(out2), and V_(out3). Capacitors 54, 55, and 56provide added filtering and improve regulator stability.

For example using a doubler for charge pump 51, linear regulators 51, 52and 53 may be used to produce any desired voltage from 1V to nearly 6V.Using a fractional charge pump to implement converter 51, the guaranteedvoltage V_(CP) is limited to below 3V since a 1.5×-mode cannot reliablyproduce a 3V output and since some voltage, typically 300 mV, is lost asa voltage drop across the linear regulator.

Furthermore, if both positive, i.e. above ground, and negative, i.e.below ground supply voltages are required by the system, the approach ofFIG. 2 cannot be employed and multiple charge pumps are required.

In summary, the limitation of today's charge pumps is that they producea single-voltage single-polarity output. While the charge pumps outputvoltage may be varied in time by mode switching, it must always delivera voltage V_(CP) higher than the highest voltage required by the system.Such restrictions greatly limit the use of charge pumps, forcingdesigners to employ one charge-pump per load, undesirably increasingcosts, component count, and printed circuit board space.

What is really needed is a multiple output charge pump voltage converteror regulator capable of producing any number of positive and negativesupply voltages simultaneously with the minimum number of components.

SUMMARY OF THE INVENTION

A multiple output DC-to-DC voltage converter using a newtime-multiplexed-capacitor converter algorithm and related circuittopologies is herein disclosed. Unlike conventional charge pumps limitedto producing a single output per charge pump, the newtime-multiplexed-capacitor topology and method generates multiplevoltage outputs of both positive and negative polarities from a singlesupply voltage or battery input. For the sake of clarity, the variousembodiments of this invention are subdivided into four classes—dualpolarity multiple-output converters, multiple-positive-outputconverters, multiple negative output converters, and re-configurablemultiple-output converters.

Dual-Polarity Time-Multiplexed-Capacitor Converters: One embodiment ofthis invention is a time-multiplexed-capacitor converter capable ofproducing positive and negative output voltages. A representativeimplementation of this embodiment includes a flying capacitor, a firstoutput node, a second output node, and a switching network. Theswitching network configured to provide the following modes of circuitoperation: 1) a first mode where the positive electrode of the flyingcapacitor is connected to an input voltage and the negative electrode ofthe flying capacitor is connected to ground; 2) a second mode where thenegative electrode of the flying capacitor is connected to the inputvoltage and the positive electrode of the flying capacitor is connectedto the first output node; and 3) a third mode where the positiveelectrode of the flying capacitor is connected to ground and thenegative electrode of the flying capacitor is connected to the secondoutput node.

The first mode of operation charges the flying capacitor to a voltageequal to the input voltage. The second mode of operation provides avoltage of twice the input voltage at the first output node. The thirdmode of operation provides a voltage equal in magnitude but opposite inpolarity to the input voltage at the second output node. Thus, apositive boosted voltage and an inverted voltage are provided using asingle multiplexed flying capacitor.

A second representative implementation of this embodiment includes afirst flying capacitor, a second flying capacitor, a first output node,a second output node, and a switching network. The switching networkconfigured to provide the following modes of circuit operation: 1) afirst mode where the first and second flying capacitors are connected inseries with the positive electrode of the first flying capacitorconnected to an input voltage and the negative electrode of the secondflying capacitor is connected to ground; 2) a second mode where thenegative electrodes of the flying capacitors are connected to the inputvoltage and the positive electrodes of the flying capacitors areconnected to the first output node; and 3) a third mode where thepositive electrodes of the flying capacitors are connected to ground andthe negative electrodes of the flying capacitors are connected to thesecond output node.

The first mode of operation charges the flying capacitor to a voltageequal to one half of the input voltage. The second mode of operationprovides a voltage of 1.5 times the input voltage at the first outputnode. The third mode of operation provides a voltage equal to −0.5 theinput voltage at the second output node. Thus, a positive boostedfractional voltage and an inverted fractional voltage are provided usingtwo multiplexed flying capacitors.

Positive Multiple Output Time-Multiplexed-Capacitor Converters: Anotherembodiment of this invention is a time-multiplexed-capacitor dual-outputconverter capable of simultaneous producing two positive fractionaloutputs +1.5V_(batt) and +0.5V_(batt) (where V_(batt) is represents theinput voltage to the charge pump). A representative implementation ofthis embodiment includes a first flying capacitor, a second flyingcapacitor, a first output node, a second output node, and a switchingnetwork. The switching network configured to provide the following modesof circuit operation: 1) a first mode where the first and second flyingcapacitors are connected in series with the positive electrode of thefirst flying capacitor connected to an input voltage and the negativeelectrode of the second flying capacitor is connected to ground; 2) asecond mode where the negative electrodes of the flying capacitors areconnected to the input voltage and the positive electrodes of the flyingcapacitors are connected to the first output node; and 3) a third modewhere the negative electrodes of the flying capacitors are connected toground and the positive electrodes of the flying capacitors areconnected to the second output node.

The first mode of operation charges the flying capacitor to a voltageequal to one half of the input voltage. The second mode of operationprovides a voltage of 1.5 times the input voltage at the first outputnode. The third mode of operation provides a voltage equal to 0.5 theinput voltage at the second output node. Thus, two positive boostedfractional voltages are provided using two multiplexed flyingcapacitors.

Multiple Negative Output Time-Multiplexed-Capacitor Converters: Inanother embodiment of this invention, a time-multiplexed-capacitordual-output converter capable of simultaneously producing two negativefractional outputs −0.5V_(batt) and −V_(batt). (where V_(batt) isrepresents the input voltage to the charge pump). A representativeimplementation of this embodiment includes a first flying capacitor, asecond flying capacitor, a first output node, a second output node, anda switching network. The switching network configured to provide thefollowing modes of circuit operation: 1) a first mode where the firstand second flying capacitors are connected in series with the positiveelectrode of the first flying capacitor connected to an input voltageand the negative electrode of the second flying capacitor is connectedto ground; 2) a second mode where the positive electrodes of the flyingcapacitors are connected to ground and the negative electrodes of theflying capacitors are connected to the first output node; and 3) a thirdmode where the first and second flying capacitors are connected inseries with the positive electrode of the first flying capacitorconnected to ground and the negative electrode of the second flyingcapacitor is connected to the second output node.

The first mode of operation charges the flying capacitors to a voltageequal to one half of the input voltage. The second mode of operationprovides a voltage of −0.5 times the input voltage at the first outputnode. The third mode of operation provides a voltage equal to −1.0 timesthe input voltage at the second output node. Thus, two invertedfractional voltages are provided using two multiplexed flyingcapacitors.

Reconfigurable Multi-Output Time-Multiplexed Fractional Charge Pumps:The time-multiplexed-capacitor charge pump can be scaled for supplyingseveral different voltages simultaneously, and can be electronicallyreconfigured to produce a different set of voltages. A representativeimplementation of this embodiment includes a first flying capacitor, asecond flying capacitor, a first output node, a second output node, athird output node, and a switching network. The switching networkconfigured to provide the following modes of circuit operation: 1) afirst mode where the flying capacitors are connected in series or inparallel between an input voltage (V_(IN)) and ground to allow theflying capacitors to be charged to any of the following voltages:V_(IN), −V_(IN), ½ V_(IN), −½ VIN; and 2) a second mode where the firstand second flying capacitors are connected in series with the negativeelectrode of the second flying capacitor connected to the input voltageand the positive electrode of the first flying capacitor is connected tothe first output node; and 3) a third mode where the negative electrodesof the flying capacitors are connected to the input voltage and thepositive electrodes of the flying capacitors are connected to the secondoutput node.

A range of different output voltages are provided to the three outputnodes depending on the configuration of the switching network duringcharging and output. At least the following combinations are available(each triple represents the output at the first output node, the voltageat the second output node and the voltage at the third output node):

1) 3V_(batt), 2V_(batt), −V_(batt),

2) 2V_(batt), 1.5V_(batt), 0.5V_(batt),

3) 2V_(batt), 1.5V_(batt), −0.5V_(batt),

4) unused, −V_(batt), −2.0_(batt),

5) unused, −0.5_(batt), −V_(batt).

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1A is a block diagram of a prior art 2×-type charge pump.

FIG. 1B is a block diagram of a prior art 1.S×-type charge pump.

FIG. 1C is a block diagram of a prior art tri-m ode 1×/I.S×/2×-typecharge pump.

FIG. 2 is a block diagram showing a charge pump supplyingmultiple-output using several linear regulators.

FIG. 3 is a block diagram of a time-multiplexed doubler/inverterdual-output charge pump.

FIG. 4A shows the operation of a doubler/inverter charge pump duringflying cap charging.

FIG. 4B shows the operation of a doubler/inverter charge pump duringcharge transfer to its +2× output.

FIG. 4C shows the operation of a doubler/inverter charge pump duringflying capacitor refresh.

FIG. 4D shows the operation of a doubler/inverter charge pump duringcharge transfer to its −1× output.

FIG. 5 is a flowchart of time-multiplexed doubler/inverter dual-outputcharge pump operation.

FIG. 6 is a state diagram describing operation of a time-multiplexeddoubler/inverter dual-output charge pump.

FIG. 7 is a graph of switching waveforms of a time-multiplexeddoubler/inverter dual-output charge pump.

FIG. 8 is a schematic of a time-multiplexedfractional/fractional-inverter dual-output charge pump.

FIG. 9A shows the operation of a fractional/fractional-inverter chargepump during flying cap charging.

FIG. 9B shows the operation of a fractional/fractional-inverter chargepump during charge transfer to its +1.5× output.

FIG. 9C shows the operation of a fractional/fractional-inverter chargepump during charge transfer to −0.5× output.

FIG. 9D is a flow chart showing the operation of a time-multiplexedfractional/fractional-inverter dual-output charge pump.

FIG. 10 is a schematic of a time-multiplexed fractionaldual-positive-output charge pump.

FIG. 11A shows the operation of a fractional dual-positive-output chargepump during flying cap charging.

FIG. 11B shows the operation of a fractional dual-positive-output chargepump during charge transfer to its +1.5× output.

FIG. 11C shows the operation of a fractional dual-positive-output chargepump during charge transfer to its +0.5× output.

FIG. 11D shows a fractional dual-positive-output charge pump using animplementation of a P-channel body bias generator.

FIG. 11E shows a fractional dual-positive-output charge pump usinggrounded N-channel MOSFETs for charge transfer.

FIG. 11F shows a fractional dual-positive-output charge pump using anisolated N-channel body bias generator.

FIG. 11G is a flow chart showing the operation of a time-multiplexedfractional dual-positive-output charge pump.

FIG. 12A shows a schematic for a −0.5×/−1× implementation of atime-multiplexed fractional dual-negative-output charge pump.

FIG. 12B shows operation of the charge pump of FIG. 12A during chargetransfer to its −0.5× output.

FIG. 12C shows operation of the charge pump of FIG. 12A during chargetransfer to its −1× output.

FIG. 12D is a flow chart showing operation of a fractionaldual-negative-output charge pump.

FIG. 12E shows modification of the flowchart of FIG. 12D for −1×/−2×outputs.

FIG. 13A shows a schematic of a time-multiplexed triple-outputfractional charge pump.

FIG. 13B is an equivalent circuit for the charge pump of FIG. 13Ashowing multiplexer operation.

FIG. 14 shows the flying-capacitor conditions for the charge pump ofFIG. 13A during operation.

FIG. 15A shows the charge pump of FIG. 13A configured for integermultiple charge transfer and operating in tripler mode.

FIG. 15B shows the charge pump of FIG. 13A configured for integermultiple charge transfer and operating in doubler mode.

FIG. 15C shows the charge pump of FIG. 13A configured for integermultiple charge transfer and operating in inverter mode.

FIG. 15D is a flow chart showing the operation of the charge pump ofFIG. 13A configured for integer multiple charge transfer.

FIG. 16A shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in doubler mode.

FIG. 16B shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in 1.5×-type fractional mode.

FIG. 16C shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in 0.5×-type fractional mode.

FIG. 16D is a flow chart showing the operation of the charge pump ofFIG. 13A configured for fractional charge transfer.

FIG. 16E shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in −0.5×-type inverting-fractional mode.

FIG. 17A shows the charge pump of FIG. 13A configured for integermultiple charge transfer and operating in −1×-type inverting mode.

FIG. 17B shows the charge pump of FIG. 13A configured for integermultiple charge transfer and operating in 1-2×-type inverting mode.

FIG. 17C is a flow chart showing the operation of the charge pump ofFIG. 13A configured for negative integer multiples of input voltage.

FIG. 18A shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in −O.S×-type inverting mode.

FIG. 18B shows the charge pump of FIG. 13A configured for fractionalcharge transfer and operating in −1×-type inverting mode.

FIG. 18C is a flow chart showing the operation of the charge pump ofFIG. 13A configured for negative fractional multiples of input voltage.

FIG. 19A is a generalized state diagram of multi-output charge pumpoperation during repeated refresh.

FIG. 19B is a generalized state diagram of multi-output charge pumpoperation during partial refresh.

FIG. 19C is a flowchart showing a method for variable charge transferfor a multi-output charge pump.

FIG. 19D is a flowchart showing an improved method for variable chargetransfer for a multi-output charge pump.

FIG. 19E is a flowchart showing a method for feedback control for amulti-output charge pump.

FIG. 20 is a block diagram of a feedback controlled multi-output chargepump.

FIG. 21 is a block diagram of a digitally controlled multi-output chargepump.

FIG. 22 is a flowchart showing a method for Interrupt driven digitallycontrol of a multi-output charge pump.

FIG. 23A is a block diagram of a digitally controlled multi-outputcharge pump with LDO pre-regulation.

FIG. 23B is a block diagram of a digitally controlled multi-outputcharge pump with LDO post-regulation.

FIG. 23C is a block diagram of a digitally controlled multi-outputcharge pump with pre and post regulation.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

A multiple output DC-to-DC voltage converter using a newtime-multiplexed-capacitor converter algorithm and related circuittopologies is herein disclosed. Unlike conventional charge pumps limitedto producing a single output per charge pump, the newtime-multiplexed-capacitor topology and method generates multiplevoltage outputs of both positive and negative polarities from a singlesupply voltage or battery input. For the sake of clarity, the variousembodiments of this invention are subdivided into four classes—dualpolarity multiple-output converters, multiple-positive-outputconverters, multiple negative output converters, and re-configurablemultiple-output converters.

Dual-Polarity Time-Multiplexed-Capacitor Converters: One embodiment ofthis invention is a time-multiplexed-capacitor converter capable ofproducing positive and negative output voltages simultaneously. In FIG.3 for example, circuit 60 illustrates a time-multiplexed-capacitordual-output converter capable of simultaneous producing doubler andinverter outputs +2V_(batt) and −V_(batt).

The converter comprises a single flying capacitor 67, MOSFETs 61 through66, and reservoir capacitors 70 and 71. Optionally MOSFETs 65 and 66 mayinclude intrinsic drain-to-source P-N diodes 68 and 69 depending onMOSFET implementation. Operation involves a sequence of fourphases—charging the flying capacitor, transferring charge to thepositive output capacitor, refreshing the flying capacitor, andtransferring charge to the negative output capacitor.

In greater detail, in the first phase of operation shown by circuit 80in FIG. 4A, also referred to herein as the charging phase, conductingMOSFETs 61 and 62 charge flying capacitor 67 to a voltage +V_(batt)through while all other MOSFETs remain off. In the schematic, thecharging current is represented by a solid line and arrow. Duringcharging, the flying capacitor's terminals are biased at V_(y)≈V_(batt)and V_(x)≈0 with diodes 68 and 69 oriented in a direction so as toremain reverse biased and non-conducting. Any current supplied to loadsconnected to either the positive or negative outputs (not shown) must bedelivered by the output capacitors 70 and 71 during this phase.

In the second phase of operation shown by circuit 85 in FIG. 4B,referred to herein as the positive charge transfer phase, MOSFETs 61 and62 are shut off and MOSFETs 64 and 65 are turned on transferring chargefrom flying capacitor to the positive output's capacitor 70 and to anyload (not shown). Current flow during charge transfer is shown by solidarrows. By virtue of conducting MOSFET 64, the negative terminal V_(x)of charged flying capacitor 67 is connected to V_(batt), so thatV_(x)=V_(batt) and diode 69 remains reverse biased and non-conducting.MOSFETs 63 and 66 remain off during this operating phase. With itsnegative terminal connected atop the battery input, the positiveterminal V_(y) of flying capacitor 67 then becomes (V_(batt)+V_(fly))charging the positive output Vouti across capacitor 70 to a positive,i.e. above ground, voltage V_(out1)→+2V_(batt).

The third phase of operation shown by circuit 90 in FIG. 4C, alsoreferred to herein as the refresh phase, is electrically identical tofirst phase 80. During capacitor refresh, conducting MOSFETs 61 and 62once again charge flying capacitor 67 to a voltage +V_(batt) throughwhile all other MOSFETs remain off. During charging, the flyingcapacitor's terminals are biased at V_(y)≈V_(batt) and V_(x)≈0 withdiodes 68 and 69 oriented in a direction so as to remain reverse biasedand non-conducting. Any current supplied to loads connected to eitherthe positive or negative outputs (not shown) must be delivered by theoutput capacitors 70 and 71 during this phase.

In the fourth and final phase of operation shown by circuit 95 in FIG.4D, referred to herein as the negative charge transfer phase, MOSFETs 61and 62 are shut off and MOSFETs 63 and 66 are turned on transferringcharge from flying capacitor 67 to the negative output's capacitor 71and to any load (not shown). Current flow during charge transfer isshown by solid arrows. By virtue of conducting MOSFET 63, the positiveterminal V_(y) of charged flying capacitor 67 is connected to ground, sothat V_(y)=0 and diode 68 remains reverse biased and non-conducting.MOSFETs 65 and 64 remain off during this operating phase. With itspositive terminal connected to the ground, the negative terminal V_(x)of flying capacitor 67 then is forced below ground to a voltage(−V_(fly)) charging the negative output V_(out2) across capacitor 71 toa negative, i.e. below ground, voltage V_(out2)→V_(batt).

The entire cycle then repeats itself as shown in flow chart 99 of FIG.5. As shown, the sequence of charge, transfer, charge, transfer with theswitches being reconfigured in between has the function of repeatedlyalternating charging the positive V_(out1) output to +2V_(batt) and thenegative V_(out2) output to −V_(batt) over time while using a singleflying capacitor to power both positive and negative outputs. The flyingcapacitor's charge transfer is therefore time multiplexed between bothoutputs, and can therefore be referred to as atime-multiplexed-capacitor multiple-output DC/DC voltage converter.

FIG. 6 illustrates the state diagram 100 for converter 60. In thecharging state 110, battery 101 is in parallel with flying capacitor 67,which charges to a voltage V_(batt). To maximize converter efficiency,the charging of capacitor 67 should preferably be completed beforeexiting state 110. Partial charging lowers overall efficiency.

During transition {circle around (1)} the converter is reconfigured forcharge transfer to the positive output, i.e. to state 111. In chargetransfer condition 111, capacitor 67 stacked atop battery 101 with itsnegative terminal V_(x) tied to the positive terminal of battery 101,charges capacitor 70 to a voltage +2V_(batt).

In one embodiment of this invention, the converter is next reconfiguredin transition {circle around (2)} back into charging state 110. Thecharging state 110 then repeats until capacitor 67 charges to a voltageV_(batt) replenishing any charge lost during state 111.

After the capacitor is refreshed, the converter is again reconfiguredduring transition {circle around (3)} into charge transfer state 112.During this state, charge flying capacitor 67 is connected below groundwith its positive terminal V_(y) connected to the negative terminal ofbattery 101. In this configuration, charge transfer from flyingcapacitor 67 to output capacitor 71 drives the negative output to avoltage equal to −V_(batt).

The converter is then reconfigured in transition {circle around (4)}back into charging state 110. The charging state 110 then repeats untilcapacitor 67 charges to a voltage V_(batt) replenishing any charge lostduring state 112.

The entire then repeats in sequence {circle around (1)} charge {circlearound (2)} positive transfer {circle around (3)} charge {circle around(4)} negative transfer and then repeating {circle around (1)}, {circlearound (2)}, {circle around (3)}, {circle around (4)}, {circle around(5)}, etc . . . . The voltage waveforms for this time multiplexedsequence is illustrated in the graphs of FIG. 7, including voltage V_(y)shown in graph 120, voltage V_(x) shown in graph 130, and voltagesV_(out1), V_(out2) and V_(fly) shown in graph 140.

From time t₀ to t₁ corresponding to state 110, flying capacitor 67 ischarged whereby V_(y) charges to V_(cc) as shown by curve 121 and V_(x)remains near ground shown by curve 131. During this cycle V_(out1) sagsbelow a value of 2V_(cc) until it reaches its minimum voltage at timet₁. In tandem, V_(out2) also sags 151 to a lower, i.e. less negative,voltage than −V_(cc).

Meanwhile V_(fly) charges during interval 145 till it reaches a voltageV_(cc) where it remains through the rest the state 110 until t₁.

During interval t₁ to t₂ corresponding to state 111, V_(x) is biased toV_(cc) during the entire cycle 132 and V_(y) is forced to 2V_(cc) asflying capacitor 67 “flies up” and transfers its charge to the positiveoutput's filter capacitor 70. As a result V_(out1) is refreshed intransition 142 while V_(fly) decays in corresponding 147.

From time t₂ to t₃ the circuit returns to state 110, flying capacitor 67is replenished as whereby V_(y) charges to V_(cc) as shown by curve 124and V_(x) remains near ground shown by curve 133. During this cycleV_(out1), now fully charged, first begins to sag 143. In tandem,V_(out2) continues to sags 151 to a lower, i.e. less negative, voltagethan −V_(cc). Meanwhile V_(fly) charges during interval 148 till itreaches a voltage V_(cc) where it remains 149 through the rest the state110 until t₃.

During interval t₃ to t₄ corresponding to state 112, V_(y) is biased toground during the entire cycle 125 and V_(x) is forced to −V_(cc) asflying capacitor 67 flies down and transfers its charge to the negativeoutput's filter capacitor 71. As a result −V_(out2) is refreshed intransition 152 stabilizing at −V_(CC) 153 while V_(fly) decays incorresponding 150. At t₄, −V_(out2) begins another cycle of decay as thecycle repeats itself.

In an alternative embodiment of this invention also shown in the statediagram of FIG. 6, transitions {circle around (2)} and {circle around(3)} are replaced by transition {circle around (5)} so that the flyingcapacitor is not refreshed between charge transfer states 111 and 112.The sequence then becomes: {circle around (1)}, {circle around (5)},{circle around (4)}, {circle around (1)} and so on.

In a related embodiment of this invention, circuit 200 of FIG. 8illustrates a time-multiplexed-capacitor dual-output converter capableof simultaneous producing positive fractional and inverting fractionaloutputs +1.5V_(batt) and −0.5V_(batt). The converter comprises a twoflying capacitors 212 and 213, a matrix of MOSFETs 201 through 211,optional P-N diodes 214 through 217, and output filter capacitors 218and 219.

As shown in the equivalent circuit 255 of FIG. 9A, operation firstinvolves charging the flying capacitors 212 and 215 through conductingMOSFETs 201, 202 and 203. Since the flying capacitors are seriesconnected each one charges to a voltage V_(batt)/2. All other MOSFETsremain off and all diodes remain reversed biased during this cycle.Output capacitors 218 and 219 must supply the current to loads 250 and251 during charging phase 255.

In the next phase shown by schematic 260 in FIG. 9B, charge istransferred from flying capacitors 212 and 213, connected in parallel,to the positive supply V_(out1), its corresponding filter capacitor 218,and to load 250. Since the negative terminals of the charged flyingcapacitors are connected to V_(batt) through on MOSFETs 205 and 207,then the positive terminal of both flying capacitors jumps to a voltageof (V_(fly)+V_(batt)) or 1.5V_(batt). With its positive terminalsconnected to output capacitor 218 through conducting MOSFETs 208 and210, the output voltage V_(out1)→+1.5V_(batt) as filter capacitor 218charges. Optionally P-N diodes 214 and 216 intrinsic to MOSFETs 208 and210 may be included depending on device construction, but must beoriented with their cathodes connected to the V_(out1) terminal. In thisphase of operation, all other MOSFETs remain off including 209 and 211.With V_(out2) negative, diodes 215 and 217 also remain reverse biased.

In a preferred embodiment, in the third phase of operation the chargepump returns the charging condition 255 of FIG. 9A where capacitors 212and 213 are each charged to V_(batt)/2. The circuit then continues intothe fourth operating phase shown by equivalent circuit 265 of FIG. 9C.In an alternate embodiment, the capacitor refresh operation can beskipped, transitioning directly from circuit 260 to 265 withoutreplenishing charge on the flying capacitors 212 and 213.

In the fourth and final phase shown by schematic 265 in FIG. 9C, chargeis transferred from flying capacitors 212 and 213, connected inparallel, to the negative supply V_(out2), its corresponding filtercapacitor 219, and to load 251. Since the positive terminals of thecharged flying capacitors are connected to ground through on MOSFETs 204and 206, then the negative terminals of both flying capacitors jumps toa voltage of (−V_(fly)) or −0.5V_(batt). With its negative terminalsconnected to output capacitor 219 through conducting MOSFETs 209 and211, the output voltage V_(out2)→−0.5V_(batt) as filter capacitor 219charges. Optionally P-N diodes 215 and 217 intrinsic to MOSFETs 209 and211 may be included depending on device construction, but must beoriented with their anodes connected to the V_(out2) terminal. In thisphase of operation, all other MOSFETs remain off including 208 and 210.With V_(out1) negative, diodes 214 and 216 also remain reverse biased.

The operation of fractional dual-output time-multiplexed-capacitorconverter 200 with a +1.5V_(batt) positive output and a −0.5V_(batt)negative output can be summarized in flow chart 299 of FIG. 9D with analgorithm of alternately charging, transferring charge to the positiveoutput, charging, and transferring charge to the negative output in amanner similar to the flow chart of FIG. 5, except that the flyingcapacitor voltage V_(fly) is increments of one-half V_(batt), i.e.fractional, rather than integer multiples. For simplicity's sake, thesteps of reconfiguring the MOSFETs between the various states are notshown explicitly.

Positive Multiple Output Time-Multiplexed-Capacitor Converters: Inanother embodiment of this invention, circuit 300 of FIG. 10 illustratesa time-multiplexed-capacitor dual-output converter capable ofsimultaneous producing two positive fractional outputs +1.5V_(batt) and+0.5V_(batt). The converter comprises a two flying capacitors 311 and312, a matrix of MOSFETs 301 through 310, optional P-N diodes 313 and314, and output filter capacitors 315 and 316.

As shown in the equivalent circuit 330 of FIG. 11A, operation firstinvolves charging the flying capacitors 311 and 312 through conductingMOSFETs 301, 302 and 303. Since the flying capacitors are seriesconnected each one charges to a voltage V_(batt)/2. All other MOSFETsremain off and all diodes remain reversed biased during this cycle.Output capacitors 315 and 316 must supply the current to loads 320 and321 during charging phase 255.

In the next phase shown by schematic 335 in FIG. 11B, charge istransferred from flying capacitors 311 and 312, connected in parallel,to the positive supply V_(out1), its corresponding filter capacitor 315,and to load 320. Since the negative terminals of the charged flyingcapacitors are connected to V_(batt) through on MOSFETs 304 and 306,then the positive terminal of both flying capacitors jumps to a voltageof (V_(fly)+V_(batt)) or 1.5V_(batt). With its positive terminalsconnected to output capacitor 315 through conducting MOSFETs 307 and309, the output voltage V_(out1)→+1.5V_(batt) as filter capacitor 315charges.

Optionally P-N diodes 313 and 314 intrinsic to MOSFETs 307 and 309 maybe included depending on device construction, but must be oriented withtheir cathodes connected to the V_(out1) terminal. In this phase ofoperation, all other MOSFETs remain off including 308 and 310. BecauseV_(out2) is also positive, MOSFETs 308 and 310 must not includeintrinsic diodes across their source to drain terminals. In oneembodiment of this invention, a special body-bias-generator circuit isemployed to eliminate the presence of the intrinsic diodes.

In a preferred embodiment, in the third phase of operation the chargepump returns the charging condition 330 of FIG. 11A where capacitors 311and 312 are each charged to Vbatt/2. The circuit then continues into thefourth operating phase shown by equivalent circuit 340 of FIG. 11C. Inan alternate embodiment, the capacitor refresh operation can be skipped,transitioning directly from circuit 335 to 340 without replenishingcharge on the flying capacitors 311 and 312.

In the fourth and final phase shown by schematic 340 in FIG. 11C, chargeis transferred from flying capacitors 311 and 312, connected inparallel, to a second positive supply V_(out2), its corresponding filtercapacitor 315, and to load 321. Since the negative terminals of thecharged flying capacitors are connected to ground through on MOSFETs 305and 303, then the positive terminals of both flying capacitors jumps toa voltage of (+V_(fly)) or +0.5V_(batt). With its positive terminalsconnected to output capacitor 315 through conducting MOSFETs 308 and310, the output voltage V_(out2)→+0.5V_(batt) as filter capacitor 315charges. In this phase of operation, all other MOSFETs remain offincluding 307 and 309. With V_(out2)<V_(out1), diodes 313 and 314 alsoremain reverse biased.

A necessary element of charge pump 300 or any a multiple positive-outputtime-multiplexed-capacitor charge pump, the charge transfer MOSFETsconnecting the flying capacitors to any output except for the mostpositive one must be free from any source-to-drain parasitic diodes ordiode conduction. Methods for eliminating source-to-drain diodeconduction as illustrated by FIGS. 11D, 11E, and 11F are described inthe following section of this application.

In summary, operation of fractional dual-outputtime-multiplexed-capacitor converter 300 with a +1.5V_(batt) and a+0.5V_(batt) positive output is shown in flow chart 369 of FIG. 11G withan algorithm of alternately charging, transferring charge to a firstpositive output, charging, and transferring charge to a second positive,then repeating the sequence. For simplicity's sake, the steps ofreconfiguring the MOSFETs between the various states are not shownexplicitly.

Method to Eliminate Unwanted Source-Drain Diodes: One key feature of atime-multiplexed-capacitor dual-positive output converter is that onlythe MOSFETs connecting the flying capacitors to the most positive outputmay include intrinsic source-to-drain diodes. Specifically in converter300, MOSFETs 308 and 310 connected to V_(out2) do not include intrinsicP-N junctions parallel to their source drain terminals, while MOSFETs307 and 309 connected to V_(out1), the most positive output voltage, do.Specifically, with their cathodes connected to the highest outputvoltage V_(out1), diodes 313 and 314 can never become inadvertentlybecome forward biased except in the second phase 335 when capacitor 315of V_(out1) is being charged. If diodes were present across 308 and 310,the charge pump voltage would be limited (V_(out2)+V_(f)), where V_(f)is the forward biased voltage of the P-N diodes, and would not functionor otherwise be able to produce its higher output voltage +1.5V_(batt).

Eliminating the P-N diode across MOSFETs 308 and 310 requires a specialtechnique incompatible with conventional source-to-body shorted MOSFETs.These methods include employing an N-channel MOSFET with a grounded bodyconnection, employing a P-channel MOSFET with its body tied to thehighest positive voltage V_(out2), or in a preferred embodiment tointegrate a special “body bias generator” circuit with either aP-channel or an N-channel MOSFET that switches source-to-drain diodepolarities to maintain reverse bias.

Such a method is illustrated in circuit 350 of FIG. 11D, where P-channelMOSFET 308 with intrinsic diodes 351A and 351B includes a body biasgenerator, or “BBG”, comprising cross coupled P-channel MOSFETs 352A and352B. The node labeled “V_(B)” represents the body or “back-gate”voltage of all three P-channel MOSFETs 308, 351A, and 351B. Operation ofthe BBG circuit involves two stable conditions as follows:

Whenever V_(CP)>V_(out2), P-channel MOSFET 352A is conducting and 352Bis off, connecting the body terminal V_(B) of PMOS 308 to V_(CP) andshorting out diode 351A. Configured in this way, diode 351B iselectrically connected in parallel to the source drain terminals ofP-channel 308. Since, the anode of diode 351B is permanently connectedto V_(OUT2) biasing its cathode to the more positive V_(CP) potentialreverse biases diode 351B and no diode conduction will occur. In thecontext of converter 300, the V_(CP)>V_(out2) condition occurs wheneverflying capacitor 311 is charged, PMOS 304 is conducting and NMOS 305 isoff, regardless of the state of MOSFET 307, a state occurring wheneverthe flying capacitor is in one of its charge transfer cycles.

Conversely, Whenever V_(OUT2)>V_(CP), P-channel MOSFET 352B isconducting and 352A is off, connecting the body terminal V_(B) of PMOS308 to V_(OUT2) and shorting out diode 351B. Configured in this way,diode 351A is electrically connected in parallel to the source drainterminals of P-channel 308. Since, the anode of diode 351A ispermanently connected to V_(CP) biasing its cathode to the more positiveV_(CP) potential reverse biases diode 351A and no diode conduction willoccur. In the context of converter 300, the V_(out2)>V_(CP) conditionoccurs whenever flying capacitor 311 is charging, PMOS 304 is off andNMOS 305 is conducting, regardless of the state of MOSFET 307, a stateoccurring whenever the flying capacitor is in one of its chargingcycles.

So using the BBG circuit technique, regardless of the polarity appliedacross P-channel MOSFET 308, the body terminal V_(B) is biased so thatno source-drain diode conduction occurs. With diode's 351A and 351B notconducting, current flow from flying capacitor 311 to output reservoircapacitor 316 is controlled by the gate voltage of MOSFET 308 and not bythe forward biasing of P-N junction diodes. In contrast to MOSFET 307with its intrinsic P-N diode 313, MOSFET 308 therefore has nosource-to-drain diode. Whenever charge pump 350 is in charge transfermode, i.e. with capacitor 311 charged and PMOS 304 conducting, currentcan be steered to either V_(OUT1) and capacitor 315, or V_(OUT2) andcapacitor 316 depending on the gate control of MOSFETs 307 and 308.Current steering is fundamental to implementing a time multiplexedcharge pump.

In circuit 350, if both MOSFETs 307 and 308 remain off, charge transferto any output can only occur by the forward biasing of diode 313. Themaximum voltage of node V_(CP) is therefore limited toV_(CP)≦(V_(out1)+V_(f)), where V_(f) is the forward biased voltage ofP-N diode 313. In a multiple positive-output time-multiplexed chargepump, only the highest most-positive voltage output can include asource-to drain diode. Any MOSFET connected to an output voltageV_(OUT2) lower, i.e. less positive, than the highest output V_(OUT1),must employ the BBG circuit to eliminate unwanted diode conduction.

As shown in circuit 350, P-channel 307 includes a parallelsource-to-drain diode 313 while PMOS 308 does not. In an alternativeembodiment diode 313 could also be eliminated by employing abody-bias-generator circuit for P-channel MOSFET 307 similar to the oneused to drive the body of P-channel 308.

Another approach is to employ an N-channel MOSFET in place of P-channel308 and optionally in place of P-channel 307. Using an N-channel MOSFETin place of a P-channel to eliminate the unwanted source-to-drainparallel diode may be implemented in one of two ways, either bypermanently grounding the N-channel MOSFET's body terminal or by using abody-bias generator technique.

In circuit 355 of FIG. 11E, P-channel MOSFET 308 has been replaced withN-channel MOSFET 356. With its body grounded, V_(B)=0 the anodes ofintrinsic diodes 357A and 357B become permanently tied to ground.Provided the source or drain terminals of N-channel MOSFET remain biasedat ground potential or above, i.e. V_(CP)≧0 and similarly V_(OUT2)≧0,then the cathodes of P-N diodes 357A and 358B will remain positive andthe diodes will remain reverse biased and non-conducting, therebyeliminating unwanted source-to-drain diode conduction in N-channelMOSFET 356. Since the body of N-channel MOSFET 356 has its body terminalgrounded, any non-isolated N-channel formed in a P-type substrate may beused to implement MOSFET 356.

In an alternative implementation N-channel MOSFET 361 is used to replaceP-channel 308. As shown, the body of N-channel 361 is not grounded andits potential V_(B) may float to a more positive voltage. Cross-coupledN-channel MOSFETs 363A and 363B along with intrinsic diodes 362A and362B form a body-bias generator circuit to bias the N-channel bodyvoltage V_(B) so that no P-N diode conduction occurs. All threeN-channel MOSFETs 361, 362A, and 362B are biased at the same potential,a voltage determined by the switching action of N-channel MOSFETs 363Aand 363B. Body bias operation is similar to that of the aforementionedBBG circuit except that N-channel MOSFETs conduct with positive gatevoltages where as the P-channel MOSFETs in circuit 350 turn-on only fornegative gate-to-source bias potentials.

As such, during the charge transfer phase when V_(CP)>V_(out2),N-channel 363B is turned on shorting-out intrinsic diode 362B andforcing V_(B)=V_(out2), the more negative of the two applied potentials.At the same time, N-channel MOSFET 363A remains off. With the cathode ofdiode 362A biased to a more positive potential V_(CP) than itsbody-connected anode biased at V_(B)=V_(out2), then diode 362A remainsreversed biased and non-conducting.

Conversely during the charging phase for flying capacitor 311 whenV_(out2)>V_(CP), N-channel MOSFET 363B is turned off and N-channel 363Aconducts, shorting-out intrinsic diode 362A and forcing V_(B)=V_(CP),the more negative of the two applied potentials. With the cathode ofdiode 362B biased to a more positive potential V_(OUT2) than itsbody-connected anode biased at V_(B)=V_(CP), then diode 362B remainsreversed biased and non-conducting. So no matter which polarity isapplied across the source-drain terminals of MOSFET 361, no P-N diodeconduction occurs.

While circuit 360 represents the N-channel circuit counterpart to theP-channel BBG circuit shown in schematic 350, monolithic integration ofN-channel version 360 into an integrated circuit requires specialconsideration. Specifically, most common CMOS integrated circuitprocesses employ a P-type substrate and a self-isolating N-type well.P-channel MOSFETs are fabricated in the N-well while N-channel areformed in the common P-type substrate or in a P-well formed in andshorted to said substrate. To implement circuit 360, however, the P-typebody of N-channels 361, 362A and 362B must be isolated from theirsurrounding P-type substrate so that V_(B) can float and is nothard-wired to ground. With a P-type body region separate from a groundedsubstrate, circuit 360 will function for any body voltages when V_(B)≧0.

Schematically, this isolation is represented by back-to-back P-N diodes364 and 365 where the anode of diode 364 represents the isolated P-typefloating region, well, or tub, the anode of diode 365 represents theP-type substrate or epitaxial layer, and the common cathode of diodes364 and 365 describe the N-type isolation at potential V_(ISO)surrounding the floating P-type region. Under normal operationV_(B)≧V_(ISO)≧0, meaning that diode 364 is forward biased and V_(ISO)will unless otherwise forced float to a positive potential approximatelyequal to V_(B), and thereby reverse bias isolation diode 365.

Multiple Negative Output Time-Multiplexed-Capacitor Converters: Inanother embodiment of this invention, circuit 370 of FIG. 12Aillustrates a time-multiplexed-capacitor dual-output converter capableof simultaneous producing two negative fractional outputs −0.5V_(batt)and −V_(batt). The converter comprises two flying capacitors 379 and380, a matrix of MOSFETs 371 through 378, optional P-N diode 381, andoutput filter capacitors 382 and 383.

As in prior fractional charge pump circuits, operation of converter 370first involves charging flying capacitors 379 and 380 through conductingMOSFETs 371, 372 and 303. Since the flying capacitors are seriesconnected each one charges to a voltage V_(batt)/2. All other MOSFETsremain off and all diodes remain reversed biased during this cycle.Output capacitors 382 and 383 must supply the current to any loads (notshown) during this charging phase.

In the next phase shown by schematic 385 in FIG. 12B, charge istransferred from flying capacitors 379 and 380, connected in parallel,to the negative supply V_(out1), its corresponding filter capacitor 382,and to its electrical load (not shown). Since the positive terminals ofthe charged flying capacitors 379 and 380 are connected to groundthrough on MOSFETs 374 and 375, then the negative terminals of bothflying-capacitors jump to a voltage of (0−V_(fly)) and −V_(batt)/2. Withits negative terminals connected to output capacitor 382 throughconducting MOSFETs 376 and 377, the output voltage V_(out1)→−0.5V_(batt)as filter capacitor 382 charges. All other MOSFETs including MOSFET 378remain off during this phase. Since V_(out2)<V_(out1), meaning V_(out2)is more negative of a potential, then with its anode connected toV_(out2), P-N diode 381 remains reverse biased and non-conducting. Butbecause V_(out2) is also negative, MOSFETs 376 and 377 must not includeintrinsic diodes across their source to drain terminals. In oneembodiment of this invention, a special body-bias-generator circuitdescribed previously in this application is employed to eliminate thepresence of the intrinsic diodes.

In a preferred embodiment, in the third phase of operation the chargepump returns the charging condition where capacitors 379 and 380 areeach charged to V_(batt)/2. The circuit then continues into the fourthoperating phase shown by equivalent circuit 386 of FIG. 12C. In analternate embodiment, the capacitor refresh operation can be skipped,transitioning directly from circuit 385 to 386 without replenishingcharge on the flying capacitors 379 and 380.

In the fourth and final phase shown by schematic 386 in FIG. 12C, chargeis transferred from flying capacitors 379 and 380, connected in series,to a second positive supply V_(out2), its corresponding filter capacitor383, and to its electrical load (not shown). Since the positive terminalof charged flying capacitor 379 is connected to ground through on MOSFET374, and the positive terminal of flying capacitor 380 is connected tothe negative terminal of flying capacitor 379 through conducting MOSFET372, then the negative terminals of flying capacitor 380 must jump to avoltage of (0-2V_(fly)) or −V_(batt). With its negative terminalconnected to output capacitor 383 through conducting MOSFETs 378 andforward biased diode 381, the output voltage V_(OUT2)→−V_(batt) asfilter capacitor 383 charges. In this phase of operation, all otherMOSFETs remain off including 376 and 377.

A necessary element of charge pump 370 or any a multiple negative-outputtime-multiplexed-capacitor charge pump the charge transfer MOSFETsconnecting the flying capacitors to any output except for the mostnegative one must be free from any source-to-drain parasitic diodes ordiode conduction. Methods for eliminating source-to-drain diodeconduction are similar to those illustrated by FIGS. 11D, 11E, and 11Ffor positive outputs, including the use of a body bias generatorcircuit.

In summary, operation of fractional dual-outputtime-multiplexed-capacitor converter 370 with a −V_(batt) and a−0.5V_(batt) negative output is shown in flow chart 389 of FIG. 12D withan algorithm of alternately charging, transferring charge to a firstnegative output, charging, and transferring charge to a second negativeoutput, then repeating the sequence. For simplicity's sake, the steps ofreconfiguring the MOSFETs between the various states are not shownexplicitly.

In converter 370, the charge transfer from the flying capacitors toV_(OUT1) shown in circuit 385 involves paralleling capacitors 379 and380. In circuit 386, during charge transfer to V_(OUT2), the capacitorsare series connected. In this regard, the parallel combination incircuit phase 385 delivers more charge to output capacitor 382 than theseries arrangement of circuit 386 is capable of delivering to V_(OUT2).This means the −0.5V_(batt) supply output V_(OUT1) is capable ofdelivering higher output currents than the −V_(batt) supply outputV_(OUT2).

In another embodiment of this invention illustrated in circuit 390 ofFIG. 12E, a modification of converter 370 produces two negative outputshaving voltages −V_(batt) and −2V_(batt), both integer multiples ofV_(batt). By adding of MOSFETs 391 and 392, both flying capacitors canbe charged to a potential of V_(batt) instead of V_(batt)/2.Specifically during charging MOSFETs 371 and 391 are turned on andcharge flying capacitor 379 to the potential V_(batt) whilesimultaneously MOSFETs 392 and 373 are turned on and charge flyingcapacitor 380 to a potential V_(batt). During charging all other MOSFETsremain off including MOSFET 372.

After charging both capacitors to V_(batt) in the first phase ofoperation, output capacitor 382 is charged during a second phase ofoperation by the parallel combination of flying capacitors 379 and 380and through conducting MOSFETs 374, 375, 376 and 377 to a voltageV_(OUT1)→−V_(batt).

After a third phase when the flying capacitors are refreshed, MOSFETs374, 372 and 378 are turned on forming a series combination ofcapacitors 379 and 380, where the positive terminal of capacitor 379 isconnected to ground, the positive terminal of capacitor 380 is connectedto the negative terminal of capacitor 379 through conducting MOSFET 372,and where the negative terminal of capacitor 380 is connected to outputcapacitor 383 which charges to V_(OUT2)→−2V_(batt).

Circuit 390 can therefore be operated in two different ways. If theflying capacitors are charged to V_(batt)/2, time multiplexingfacilitates two output voltages, namely −V_(batt)/2 and −V_(batt). Ifthe flying capacitors are instead charged to V_(batt), time multiplexingfacilitates two higher output voltages, namely −V_(batt) and −2V_(batt).Because the converter is producing two outputs of the same polarity,MOSFETs 376 and 377 must be free of any parasitic source-to-draindiodes.

Reconfigurable Multi-Output Time-Multiplexed Fractional Charge Pumps:The time-multiplexed-capacitor charge pump can be scaled for supplyingseveral different voltages simultaneously, and can be electronicallyreconfigured to produce a different set of voltages. For example, FIG.13A illustrates a triple-output reconfigurable charge pump 400comprising flying capacitors 410 and 411, MOSFETs 401 through 409 and412 through 417, output filter capacitors 424, 425 and 426, and bodybias generator circuits 419, 420, 422 and 423. Intrinsic diodes 418 and421 corresponding to MOSFETs 412 and 415 respectively are also includedbut may alternatively be substituted by BBG circuits.

The circuit topology of converter 400 comprises two H-bridges, one foreach flying capacitor, a MOSFET for connecting the flying capacitors inseries, and two MOSFET “triplets” used for control charge transfer tothe converters three voltage outputs V₁, V₂, and V₃. In greater detail,capacitor 410 is biased at node voltages V_(z) and V_(y) where nodeV_(z) is driven by a push-pull buffer comprising Vbatt-connected MOSFET401 and grounded MOSFET 402, and where V_(y) is driven by a push-pullbuffer comprising V_(batt)-connected MOSFET 405 and grounded MOSFET 406.Together MOSFETs 401, 402, 405 and 406 form an H-bridge drivingcapacitor 410.

Similarly, capacitor 411 is biased at node voltages V_(x) and V_(w)where node V_(x) is driven by a push-pull buffer comprisingV_(batt)-connected MOSFET 403 and grounded MOSFET 404, and where V_(w)is driven by a push-pull buffer comprising V_(batt)-connected MOSFET 407and grounded MOSFET 408. Together MOSFETs 403, 404, 407 and 408 form anH-bridge driving capacitor 411. Node V_(x) of capacitor 411 is alsoconnected to node V_(y) of capacitor 410 by MOSFET 409.

Charge-transfer MOSFETs 412, 413, and 414 together form a tripletconnecting node V_(z) of flying capacitor 410 to outputs V₁, V₂ and V₃respectively. Similarly, charge-transfer MOSFETs 415, 416, and 416together form a triplet connecting node V_(x) of flying capacitor 411 tooutputs V₁, V₂ and V₃ respectively. Outputs V₁, V₂ and V₃ correspond tofilter capacitors 424, 425, and 426 respectively.

Operation of the MOSFET array can better be interpreted as a series ofmultiplexer switches, although the MOSFETs may in some circumstances beused to control capacitive charging currents. This functionalinterpretation of charge pump 400 is illustrated in circuit 430 of FIG.13B, comprising for sets of single-pole triple-throw, or SP3T, switches431, 432, 433, and 434: and two SP4T, i.e. single-pole four-throw,switches 435 and 436; flying capacitors 410 and 411; output caps 424through 426; and optional diodes 418 and 421.

MOSFETs 401 and 402 comprise 1P3T switch 431 which in operation selectsone of three inputs, V_(batt) when MOSFET 401 is on, ground when MOSFET402 is in its on state, or an open circuit when neither MOSFETs 401 or402 are conducting. The output of multiplexer switch 431 biases nodeV_(z) on flying capacitor 410. A second 1P3T switch 432 comprisesMOSFETs 405 and 406, and in operation biases node V_(y) on capacitor410. In a similar configuration for biasing capacitor 411, MOSFETs 403and 404 comprise 1P3T multiplexer switch 433 biasing node V_(x) onflying capacitor 411. A second 1P3T switch 434 comprises MOSFETs 407 and408, and in operation biases node V_(w) on capacitor 411. MOSFET 409 isincluded for connecting capacitors 410 and 411 in series when needed.

The output of the node voltages V_(z) and V_(x) are selected and timemultiplexed to supply energy to one of several outputs V₁, V₂ or V₃,transferring charge from flying capacitors 410 and 411 to outputcapacitors 424, 425, and 426. SP4T switch 435 is formed from the MOSFETtriplet comprising devices 412, 413 and 414. SP4T switch 436 is formedfrom the MOSFET triplet comprising devices 415, 416 and 417. In apreferred embodiment each MOSFET triplet has only one device conductingat a time. The no-connect or NC switch position corresponds to the statewhere all three MOSFETs are off.

Operation is similar to the previous examples except that there are agreater number of combinations of inputs and outputs possible, primarilydue to the flexible reconfigurable MOSFET matrix. Operation involvescharging the flying capacitors, transferring charge to output V₁ and itscapacitor 424, refreshing the flying capacitors, transferring charge tooutput V₂ and its capacitor 425, refreshing the flying capacitors again,transferring charge to output V₃ and its capacitor 426, then repeatingthe entire sequence again.

Charging of the flying capacitors can be achieved in many ways usingconverter 400. A few of these combinations are illustrated in FIG. 14.In equivalent circuit 450, capacitors 410 and 411 are each charged to avoltage V_(batt) where MOSFET 401 is on, V_(z)=V_(batt), MOSFET 406 ison, V_(y)=0 and MOSFET409 is off. Simultaneously, MOSFET 403 is on,V_(x)=V_(batt), MOSFET 408 is on, and V_(w)=0. All other MOSFETs areoff. This condition corresponds to having multiplexers 431 and 433 intheir V_(batt) position and multiplexers 432 and 434 in their groundedposition. The flying capacitors are therefore charged in parallel toeach other and equal in voltage to the battery input.

In equivalent circuit 460, capacitors 410 and 411 are each charged to avoltage V_(batt)/2 where MOSFET 401 is on, V_(z)=V_(batt), MOSFET 409 ison, V_(y)=V_(x), MOSFET408 is on, and V_(w)=0. All other MOSFETs areoff. This condition corresponds to having multiplexers 431 in itsV_(batt) position, multiplexers 432 and 433 in its NC position, andmultiplexer 434 in its grounded position. The flying capacitors aretherefore charged in series with one other and equal in voltage toone-half the battery input voltage.

In both charging circuits 450 and 460, the positively charged capacitorplates are connected to V_(z) and V_(x). The conditions V_(z)>V_(y) andV_(x)>V_(w) are defined herein as positive polarity charging. The MOSFETmatrix and multiplexer can also charge capacitors in inverted polarity.In schematic 470, node V_(z) and V_(x) are biased to ground byconducting MOSFETs 402 and 404 while V_(y) and V_(w) are biased toV_(batt) by on-state MOSFETs 405 and 407. As shown, flying capacitors410 and 411 are charged in parallel but opposite in polarity relative tocondition 450, i.e. they are charged to −V_(batt). MOSFET 409 and allother devices remain off during charging.

Circuit 480 represents the fractional inverted charging condition whereV_(z) is biased to ground by on MOSFET 402; V_(w) is biased to V_(batt)by conducting MOSFET 407, and on-state MOSFET 409 forces V_(x)=V_(y).Being series connected, each flying capacitor charges to half thebattery voltage but relative to circuit 460, in inverted polarity, i.e.the capacitors are charge to a bias of −V_(batt)/2. Other chargingconditions, e.g. where flying capacitor 410 is charge to a positivepolarity while flying capacitor 411 is charged in its inverted polarity,also exist but are not included in the drawings.

By charging the flying capacitors to the battery input bias V_(batt),time multiplexed converter 400 can output two positive voltages and onenegative voltage simultaneously, where the voltages comprise 3V_(batt),2V_(batt) and −V_(batt). FIG. 15A illustrates tripler 500 charge pumpoperation during charge transfer to output V₁ where the two flyingcapacitors, each charged to V_(batt), are stacked on top one another andconnected on top of the battery input by conducting MOSFETs 407, 409 and412. Forward biased diode 418 in conjunction with conducting MOSFET 412charges output capacitor 424 to a voltage 3V_(batt). All other MOSFETsincluding MOSFET 415 remain off. Because V_(oou1) represents the mostpositive output voltage diode 421 remains reversed biased andnon-conducting. The node voltages of circuit 500 compriseV_(w)=V_(batt), V_(x)=V_(y)=2V_(batt), and V_(z)=V_(out)=2V_(batt).

FIG. 15B illustrates doubler 510 charge pump operation during chargetransfer to output V₂ where the two flying capacitors, each charged toV_(batt), are connected in parallel and stacked on top of the batteryinput using conducting MOSFETs 405, 407, 413 and 416. Conducting MOSFETs413 and 416 transfer their charge to capacitor 425 corresponding tooutput voltage of 2V_(batt). All other MOSFETs including MOSFET 409remain off. Because V_(out2) is not the most positive output voltage,MOSFETs 413 and 416 must utilize BBG circuitry 419 and 422 to preventunwanted diode conduction.

FIG. 15C illustrates inverter 520 charge pump operation during chargetransfer to output V₃ where the one flying capacitor, charged toV_(batt), is biased below ground using conducting MOSFETs 402, 409, and417. Conducting MOSFETs 417 transfers its charge to capacitor 426corresponding to output voltage of −V_(batt). All other MOSFETsincluding MOSFET 408 remain off. Because V₃ is not the most positiveoutput voltage, MOSFETs 417 must utilize BBG circuitry 423 to preventunwanted diode conduction. Capacitor 411 pre-charged to V_(batt) is notcharged, discharged or otherwise affected in this operating mode. Thecorresponding flow algorithm for the triple-output time-multiplexedcapacitor charge pump with dual polarity output is shown in FIG. 15D.

FIG. 16A illustrates doubler charge pump 530 operation during chargetransfer to output V₁ where the two flying capacitors, each charged toV_(batt)/2 are stacked on top one another and connected on top of thebattery input by conducting MOSFETs 407, 409 and 412. Forward biaseddiode 418 in conjunction with conducting MOSFET 412 charges outputcapacitor 424 to a voltage 2V_(batt). All other MOSFETs including MOSFET415 remain off. Because V_(out1) represents the most positive outputvoltage diode 421 remains reversed biased and non-conducting. The nodevoltages of circuit 530 comprise V_(w)=V_(batt),V_(x)=V_(y)=1.5V_(batt), and V₂=V_(out)=2V_(batt).

FIG. 16B illustrates fractional charge pump 540 operation during chargetransfer to output V₂ where the two flying capacitors, each charged toV_(batt)/2, are connected in parallel and stacked on top of the batteryinput using conducting MOSFETs 405, 407, 413 and 416. Conducting MOSFETs413 and 416 transfer their charge to capacitor 425 corresponding tooutput voltage of 1.5V_(batt). All other MOSFETs including MOSFET 409remain off. Because V_(out2) is not the most positive output voltage,MOSFETs 413 and 416 must utilize BBG circuitry 419 and 422 to preventunwanted diode conduction.

FIG. 16C illustrates fractional charge pump 550 operation during chargetransfer to output V₃ where the two flying capacitors, each charged toV_(batt)/2, are connected in parallel and connected on top of the groundpotential using conducting MOSFETs 406, 408, 414 and 417. ConductingMOSFETs 414 and 417 transfer their charge to capacitor 426 correspondingto output voltage of 0.5V_(batt). All other MOSFETs including MOSFET 409remain off. Because V_(out3) is not the most positive output voltage,MOSFETs 414 and 417 must utilize BBG circuitry 420 and 423 to preventunwanted diode conduction. The corresponding flow algorithm 559 for thefractional triple-output time-multiplexed capacitor charge pump is shownin FIG. 16D.

FIG. 16E illustrates the limitation of converter 400 in producing afractional negative output voltage −0.5V_(batt) from a capacitor chargedto a positive 0.5V_(batt). The complication comes from the fact thatboth flying capacitors 410 and 411 must be charged to be biased toV_(batt)/2. In the charge transfer circuit 560 of FIG. 16E however,capacitor 411 remains floating. While MOSFETs 402 409 and 417 create apath to transfer charge from flying capacitor 410 to output 426,capacitor 411 can not have its positive terminal biased to ground orconnect V_(w) to the output without the need for additional MOSFETcircuitry. One solution is to discharge capacitor 410 before chargingrefreshing capacitor 410, but this action lowers efficiency of theconverter.

FIG. 17A illustrates inverter 570 charge pump operation during chargetransfer to output V₂ where the two flying capacitor, both charged toV_(batt), are connected in parallel and biased below ground usingconducting MOSFETs 406, 408, 413 and 416. Conducting MOSFETs 413 and 416transfer their charge to capacitor 425 corresponding to output voltageof −V_(batt). All other MOSFETs including MOSFET 409 remain off. Asshown, MOSFETs 413 and 422 utilize BBG circuitry 419 and 422 to preventunwanted diode conduction.

FIG. 17B illustrates inverter 590 charge pump operation during chargetransfer to output V₃ where the two flying capacitor, both charged toV_(batt), are connected in series and biased below ground usingconducting MOSFETs 408, 409, and 414. Conducting MOSFETs 414 transfersits charge to capacitor 426 corresponding to output voltage of−2V_(batt). All other MOSFETs including MOSFET 417 remain off. As shown,MOSFET 414 utilizes BBG circuitry 423 to prevent unwanted diodeconduction. The corresponding flow algorithm 599 for the dual-outputtime-multiplexed capacitor charge pump with inverting outputs is shownin FIG. 17C.

FIG. 18A illustrates inverter 600 charge pump operation during chargetransfer to output V₂ where the two flying capacitor, both charged toV_(batt)/2 are connected in parallel and biased below ground usingconducting MOSFETs 406, 408, 413 and 416. Conducting MOSFETs 413 and 416transfer their charge to capacitor 425 corresponding to output voltageof −V_(batt)/2. All other MOSFETs including MOSFET 409 remain off. Asshown, MOSFETs 413 and 422 utilize BBG circuitry 419 and 422 to preventunwanted diode conduction.

FIG. 18B illustrates inverter 610 charge pump operation during chargetransfer to output V₃ where the two flying capacitor, both charged toV_(batt)/2, are connected in series and biased below ground usingconducting MOSFETs 408, 409, and 414. Conducting MOSFETs 414 transfersits charge to capacitor 426 corresponding to output voltage of−V_(batt). All other MOSFETs including MOSFET 417 remain off. As shown,MOSFET 414 utilizes BBG circuitry 420 to prevent unwanted diodeconduction. The corresponding flow algorithm 619 for the dual-outputtime-multiplexed-capacitor charge pump with fractional inverting outputsis shown in FIG. 18C.

Algorithmic Considerations in Time-Multiplexed-Capacitor Charge Pumps.Regardless of the voltage, polarity, and number of outputs, timemultiplexing of a charge pump follows a simple algorithm 700 shown inFIG. 19A. This algorithm involves the steps of charging the flyingcapacitors, transferring charge from the flying capacitors to a firstoutput at voltage V₁, returning to the original state 701 and refreshingthe flying capacitor's charge, transferring charge from the flyingcapacitors to a second output at voltage V₂, returning to the originalstate 702 and refreshing the flying capacitor's charge, transferringcharge from the flying capacitors to a third output at voltage V₃,returning to the original state 703 and refreshing the flyingcapacitor's charge, and so on up to “n” states, then repeating themultiplexing sequence. This sequence is shown by the solid lines andarrows in flow chart 700.

The dotted lines and arrows in flow chart 700 represent an alternativeflow where the flying capacitors are not refreshed between chargetransfers but instead charge several output capacitors before returningto refresh the flying capacitors. Specifically in such an algorithm, theconverter charges the flying capacitors, transfers charge from theflying capacitors to a first output at voltage V₁, then followingtransition 704 transfers charge from the flying capacitors to a secondoutput at voltage V₂, followed by transition 705 transferring chargefrom the flying capacitors to a third output at voltage V₃, and onlythereafter returns by transition 706 to refresh the flying capacitors.

While either algorithm, the theoretical number of converted voltages maybe adapted for “n” outputs. One limitation of this approach is outputripple increases in proportion with “n”, the number of outputs—thegreater the number of outputs, the greater the output ripple of anygiven output will be. Also any algorithm that doesn't regularly refreshthe flying capacitors will suffer more voltage sag on the flyingcapacitors, which in turn further degrades ripple. Conversely,refreshing the flying capacitors more often reduces the frequency bywhich a given output's filter capacitor is refreshed.

In one embodiment of this invention, ripple is minimize by matching thealgorithm to the output's ripple requirements, i.e. choosing analgorithm where the outputs charged last or the least often power loadsthat tolerate the highest degree of ripple. In the dotted line algorithmof state diagram 700 comprising transitions 704, 705, and 706, forexample, the flying capacitors exhibit their greatest voltage sag duringcharge transfer to the V₃ output capacitor, the last output to berecharged before the flying capacitors are refreshed by transition 706.As such the ripple specification for V₃ should be worse than V₂ and theload and specification should be matched accordingly. In comparison, theV₁ output, the first charge transfer after refreshing the flyingcapacitors, will exhibit the lowest ripple. Ripple may be also bereduced by increasing the size of the output capacitors, but with thedisadvantage of some incremental cost.

One compromise to the tradeoff between voltage sag in the flyingcapacitors versus recharge rate of a specific output voltage is shown inFIG. 19B. In algorithm 720, four outputs V₁ through V₄ are powered by atime-multiplexed-capacitor charge pump. As shown, after charging theflying capacitors and supplying charge to the V₁ output capacitor, statechange 721 then supplies charge to the V₂ output capacitor beforereturning to the condition to refresh the flying capacitors. Afterrefreshing the flying capacitors transition 723 powers the V₃ outputcapacitor, followed by transition 724 to transfer charge to the V₄output capacitor, the converter then returns by transition 725 back toits initial state. The entire cycle repeats itself.

As is often the case in electronic systems not every power supply mustmeet strict ripple and regulation requirements, often because someelectrical loads are tolerant to noise or do not exhibit significantcurrent transients. In the event that some outputs exhibit larger loadcurrent transients than others, the algorithm can be adjusted tore-charge noisy and changeable outputs more often. Such an algorithm isrepresented in flow chart 740 of FIG. 19C where the V₁ output capacitoris refreshed twice per cycle, charge transfer steps 741 and 742, whilethe V₂ output is charged only once. In this algorithm however, V₂ ischarged from flying capacitors which may have sagged from the chargetransfer operation 742 immediately preceding it.

In an alternate algorithm 760 shown in FIG. 19D, the flying capacitorsare refreshed 761 just prior to charge transfer to the V₂ output toreduce V_(fly) voltage sag. Like algorithm 740 however, the V₁ outputcapacitor is re-charged from the flying capacitors at twice the rate ofthe V₂ output capacitor.

The disadvantage of all the aforementioned algorithms is theyredistribute energy from the flying capacitors to the variousmultiplexed outputs without any consideration of load conditions. Suchalgorithms exhibit “blind distribution” of the converter's energyallocation. While it is true that the various voltage outputs will nottransfer charge from the flying capacitors to their output capacitorunless it is needed, a fixed time is none-the-less allocated to do so.Meanwhile other outputs experiencing large load current transients andvoltage deviations cannot react and are not allocated longer transfertimes in order to react more quickly. Conversely, however, variablecharge transfer times for each output will result in variable frequencyoperation and a varying noise spectrum—an undesirable characteristic inmany electronic systems, especially those related to communication.

A fixed frequency algorithmic method remedies this problem whereby, inan alternative embodiment of the invention, a time-multiplexed-capacitormultiple output charge pump uses feedback to dynamically adjust theconverter's algorithm to respond to rapid charge in the load conditionof specific voltage outputs. Algorithm 780 shown in FIG. 19E describes atime-multiplexing technique where the output capacitor for a critical V₁output is recharged multiple times until the output voltage is within aspecified tolerance.

The conditional test 781 determines whether another charge pump cycle ofcharging the flying capacitors and transferring charge to the V₁capacitor is needed or if normal operation may resume, where the V₂output capacitor is to be charged in alternating sequence with the V₁output. This conditional test requires monitoring of the V₁ outputvoltage either by using an analog comparator or by using digital controlfed by an analog-to-digital converter, herein referred to as by theacronym ADC or A/D.

Conditional test 782 insures that V₂ occasionally is re-charged evenduring a V₁ load transient. Counter 783 counts the number of times theflying capacitors transfer charge to the V₁ output. So long that thecounter does not exceed some pre-defined value “n”, which may forexample be 2, 3, or many more times, then the charge pump will continueto refresh the flying capacitors and transfer its charge to the V₁output capacitor. If the count does, however, exceed “n” then theconverter is diverted to re-charge V₂, even though V₁ has not yetreached its defined tolerance range. Each time that a charge transfer toV₂ occurs, the counter is reset to zero by step 784 and the entire cyclerepeated.

Under normal operation, algorithm 780 charges the V₁ and V₂ outputcapacitors in alternating fashion. While compatible with variablefrequency operation, algorithm 780 works equally well with fixedfrequency charge pump operation. In the event of a V₁ load transient,the system adapts to deliver more charge to the critical output byincrementing the charge transfer to V₁ by some integer number of cycles.In a preferred embodiment this adaptive response still occurs at a fixedclock rate. Algorithm 780 evaluates the condition of V₁ every chargingcycle.

The algorithm 780 can be similarly modified for three or more outputvoltages V₁, V₂, and V₃ as shown in circuit 790 of FIG. 20 combiningcharge pump 791, time multiplexed capacitors 795 and 796, and outputcapacitors 792, 793, and 794. If only output V₁ is sensitive to loadtransients, the system hardware can be implemented with a voltagereference 798 and comparator 797 to provide feedback to the logic insidethe time multiplexed charge pump 791.

If two voltages require feedback for improved response time, a secondcomparator 799 can be added, but consideration must be given to thehierarchical priority given to each voltage output in the algorithm. Forexample if the highest priority is given to V₁ and re-charging capacitor792, then V₂ and V₃ will exhibit slower transient response times, whichmay be offset in part by using higher capacitance filter capacitors 793and 794. Alternatively comparator 797 can be time multiplexed to monitorboth V₁ and V₂ outputs on a sample rather than a continuous basis. Theapproach where an algorithm constantly or frequently requests physicalinformation, in this case the charge pump's output voltages, on aregular basis is known as a “polled” system.

Since many of the algorithms described contain “if-then-else” decisions,another option is to implement the priority hierarchy and multiplexingalgorithm using firmware implemented in a microprocessor based system.FIG. 21 illustrates system 810 including a microprocessor ormicrocontroller 814, time-multiplexed-capacitor charge pump 811 withcapacitors 812 and 813, voltage regulator 815, output capacitors 819,818 and 817 corresponding to outputs V₁, V₂ and V₃ respectively, clock816, analog multiplexer 820, analog-to-digital converter 821 andinterrupt generation circuit comprising comparator 623, voltagereference 822, and N-channel MOSFET 824.

Basic operation of triple output charge pump 811 remains under thecontrol of microprocessor 814 which monitors the voltages on outputs V₁and V₂ on a sample basis and adjusts the algorithm dynamically toimprove transient response. Analog multiplexer facilitates monitoringtwo different outputs from one A/D converter 821 and to report thedigital information into digital inputs of microprocessor 814. Bothmicroprocessor 814 and charge pump 811 are powered from voltageregulator 815 and are synchronized to a common clock switching atfrequencies φ and m·φ respectively. The multiplier m can be 0.001meaning the charge switches at a rate three orders-of-magnitude lessthan the processor.

The interrupt circuit reduces the overhead needed for monitoring thevoltage conditions of V₁ and V₂ outputs. Rather than forcing themicroprocessor to constantly monitor the output of A/D converter 821,comparator 823 generates an interrupt whenever V_(mux), the sample ofeither V₁ or V₂ outputs, drops outside a specified range. By turning onMOSFET 824, the INT interrupt pin on the microprocessor is pulled down,and invokes an event-driven interrupt. Only during the interrupt serviceroutine, does the microprocessor need to look at or analyze the outputof A/D converter 821.

The concept of an interrupt driven change in the control algorithm isillustrated in the exemplary flow chart 850 of FIG. 22. If no interrupthas occurred the charge pump operates according to thetime-multiplexed-capacitor charge pump algorithm 851 describedpreviously. If however, an INT interrupt occurs the program will jump toits ISR, i.e. its interrupt service routine 852. Once there it givespriority to the V₁ output by recharging its output then as needed itcharges the V₂ output capacitor. Every loop of the ISR code, the flyingcapacitors charge output V₁ and optionally, charge output V₂ only asneeded. When V₁ finally reaches its final tolerance range, conditionaltest 853 end the interrupt routine 852, clears the interrupt hardware854 and reinitiates normal algorithm 851.

To prevent degradation of other regulated outputs other than thepriority outputs V₁ and V₂ during the ISR routine 852, initiation of aninterrupt clears a counter 856 and increments it by one each timethrough the loop as shown by operation 857. When the counter finallyexceeds n times as determined by conditional 855, the algorithm jumpsfrom the ISR loop 852 to charge V₂ and V₃ without resetting theinterrupt. Once the charge transfer to V₃ has occurred the interruptdetect 858 will determine that V₁ is not yet compliant with itstolerance range and the converter will jump back to ISR tasks 852.

The algorithm can be adjusted in numerous ways depending on the mix ofpositive and negative supply voltages produced by the multiple outputcharge pump.

Regulating Multiple Charge-Pump Voltages; Charge pumps do not regulatevoltage, but instead produce a time varying output that represents somefixed multiplier of the input voltage. The time-multiplexed-capacitormultiple output charge pump is no different in this regard. Moreovercharge pumps are only efficient when the load voltage operates near thecharge pump's nX multiple.

One common way to eliminate voltage variation in a charge pump's outputis to combine it with a low drop-out linear regulator or LDO. Likeconventional charge pumps, time-multiplexed-capacitor multiple outputcharge pump disclosed herein can also be combined with LDOs used toprovide either pre-regulation to the charge pump, to provide postregulation, or both.

For example in system 880 of FIG. 23A, LDO regulator 883 acts as apre-regulator to time-multiplexed charge pump 885. The LDO regulatesLilon battery 881 to a constant intermediate voltage V_(y) across filtercapacitor 884 which is necessarily less than V_(batt). The intermediatevoltage Vy is then input into a single time-multiplexed charge pump toproduce 885 with flying capacitors 886 and 887 to output three regulatedoutputs V₁, V₂ and V₃ with corresponding filter capacitors 888, 889, and890. The output voltages are given by fixed fractional or integermultiples n₁, n₂, and n₃ by the relations:

V ₁ =n ₁ ·V _(y)

V ₂ =n ₂ ·V _(y)

V ₃ =n ₃ ·V _(y)

Multiples of n include −2×, −1×, −0.5×, +0.5×, +1.5×, +2×, and +3×. Fora lithium ion battery V_(y) is likely 3V or 2.7V in order to maximizeoperation over the full battery discharge life of 4.2V down to 3V.

In an alternative embodiment, system 900 of FIG. 23B includes anun-regulated charge pump 903 with a time varying input voltage V_(batt)from battery 901. The time-multiplexed charge pump 903 with flyingcapacitors 904 and 905 produces three un-regulated outputs V₁, V₂ and V₃with corresponding filter capacitors 906, 907, and 908. These voltagesact as inputs to LDOs 909, 910, and 911 to produce outputs V₅, V₆ and V₇with corresponding filter capacitors 912, 913, and 914.

While the intermediate voltages V₁, V₂ and V₃ are given by fixedfractional or integer multiples n₁, n₂, and n₃, the output voltages V₅,V₆ and V₇ are determined by the LDO circuit and not the charge pump withone caveat, that the LDO's input must be higher than its output. Inother words, the voltages the input to LDO 909 must be higher than itsoutput so that V₁>V₅, the input to LDO 910 must be higher than itsoutput so that V₂>V₆, and the input to LDO 911 must be higher than itsoutput so that V₃>V₇.

In some instances not every output needs dedicated regulation. Onesolution to that scenario shown in schematic 940 of FIG. 23C is toutilize a single LDO 943 as a pre-regulator, atime-multiplexed-capacitor charge pump 945 to produce multiple outputsupplies V₁, V₂ and V₃ with corresponding filter capacitors 948, 951 and952 and then to selectively post regulate certain outputs as need be. Inthis example LDO 949 is used to regulate voltage V₁ to a lower voltageV₅ filtered by capacitor 950.

As another embodiment of this invention, a time-multiplexed-capacitorcharge pump can produce multiple independent outputs having the samevoltage. Such a need arises when the same supply voltage is used formultiple purposes, e.g. for power, digital, analog and RF circuitry. Toavoid noise and interference the supplies can be separated. For example,in circuits 880, 900 or 940, it is possible for V₁=V₂ while V₁≠V₃ usingthe disclosed time-multiplexing charge pump methods described herein.

For example in FIG. 13A and 13B, after charging each capacitor to avoltage V_(batt), the charge transfer from flying capacitors 410 and 411to the outputs V₁ and to V₂ could both be configured in the 2×, ordoubler, mode. Referring to FIG. 15B, MOSFETs 405 and 407 connect thenegative terminals of flaying capacitors 410 and 411 to positiveterminal of the battery, so that V_(w)=V_(y)=V_(batt). Turning onMOSFETs 413 and 416, routes the charge from flying capacitors 410 and411 to output capacitor 425 and V₂. If instead, MOSFETs 412 and 415 wereturned on, the charge would be routed to output capacitor 424 and V₁.

So by successively charging the outputs V₁ and V₂ with the same bias,two independent outputs operating of the same voltage can generated, sothat V₁=V_(batt) and V₂=V_(batt) but V₁ and V₂ are completelyindependent supplies.

I claim:
 1. A multiple output charge pump comprising: a flying capacitorhaving a positive electrode and a negativeelectrode; a first outputnode; a second output node; and a switching network configured toprovide a first mode, a second mode, and a third mode.
 2. The chargepump of claim 1 wherein for the first mode the positive electrode of theflying capacitor is connected to an input voltage and the negativeelectrode of the flying capacitor is connected to ground.
 3. The chargepump of claim 2 wherein for the second mode the negative electrode ofthe flying capacitor is connected to the input voltage and the positiveelectrode of the flying capacitor is connected to the first output node.4. The charge pump of claim 3 wherein for third mode the positiveelectrode of the flying capacitor is connected to ground and thenegative electrode of the flying capacitor is connected to the secondoutput node.
 5. The charge pump of claim 4 further comprising: a firstMOSFET connected between the positive electrode of the flying capacitorand the input voltage; a second MOSFET connected between the negativeelectrode of the flying capacitor and ground; a third MOSFET connectedbetween the positive electrode of the flying capacitor and the firstoutput node; and a fourth MOSFET connected between the negativeelectrode of the flying capacitor and the second output node,
 6. Thecharge pump of claim 5 further comprising a control circuit that drivesthe first, second, third, and fourth MOSFETs so that the first, second,and third modes are selected in a repeating sequence.
 7. The charge pumpof claim 6 wherein the repeating sequence is first mode, second mode,first mode, third mode.
 8. The charge pump of claim 6 wherein therepeating sequence is first mode, second mode, third mode.
 9. A multipleoutput charge pump comprising: a first flying capacitor having apositive electrode and a negative electrode; a second flying capacitorhaving a positive electrode and a negative electrode; a first outputnode; a second output node; and a switching network configured toprovide a first mode where the first and second flying capacitors areconnected in series, a second mode, and a third mode.
 10. The chargepump of claim 9 wherein for the first mode the positive electrode of thefirst flying capacitor is connected to an input voltage and the negativeelectrode of the second flying capacitor is connected to ground.
 11. Thecharge pump of claim 10 wherein for the second mode the negativeelectrodes of the flying capacitors are connected to the input voltageand the positive electrodes of the flying capacitors are connected tothe first output node.
 12. The charge pump of claim 11 wherein for thethird mode the positive electrodes of the flying capacitors areconnected to ground and the negative electrodes of the flying capacitorsare connected to the second output node.
 13. The charge pump of claim 12further comprising a control circuit that drives the switching networkso that the first, second, and third modes are selected in a repeatingsequence.
 14. The charge pump of claim 13 wherein the repeating sequenceis first mode, second mode, first mode, third mode.
 15. The charge pumpof claim 13 wherein the repeating sequence is first mode, second mode,third mode.
 16. A multiple output charge pump comprising: a first flyingcapacitor having a positive electrode and a negative electrode; a secondflying capacitor having a positive electrode and a negative electrode; afirst output node; a second output node; and a switching networkconfigured to provide a first mode where the first and second flyingcapacitors are connected in series, a second mode, and a third mode. 17.The charge pump of claim 16 wherein for the first mode the positiveelectrode of the first flying capacitor is connected to an input voltageand the negative electrode of the second flying capacitor is connectedto ground.
 18. The charge pump of claim 17 wherein for the second modethe negative electrodes of the flying capacitors are connected to theinput voltage and the positive electrodes of the flying capacitors areconnected to the first output node.
 19. The charge pump of claim 18wherein for the third mode the negative electrodes of the flyingcapacitors are connected to ground and the positive electrodes of theflying capacitors are connected to the second output node.
 20. Thecharge pump of claim 16 further comprising a control circuit that drivesthe switching network so that the first, second, and third modes areselected in a repeating sequence.
 21. The charge pump of claim 20wherein the repeating sequence irst mode, second mode, first mode, thirdmode.
 22. The charge pump of claim 20 wherein the repeating sequence isfirst mode, second mode, third mode.
 23. A multiple output charge pumpcomprising: a first flying capacitor having a positive electrode and anegative electrode; a second flying capacitor having a positiveelectrode and a negative electrode; a first output node; a second outputnode; and a switching network configured to provide a first mode wherethe first and second flying capacitors are connected in series, a secondmode, and a third made.
 24. The charge pump of claim 23 wherein for thefirst mode the positive electrode of the first flying capacitor isconnected to an input voltage and the negative electrode of the secondflying capacitor is connected to ground.
 25. The charge pump of claim 24wherein for the second mode the positive electrodes of the flyingcapacitors are connected to ground and the negative electrodes of theflying capacitors are connected to the first output node.
 26. The chargepump of claim 25 wherein for the third mode the first and second flyingcapacitors are connected in series with the positive electrode of thefirst flying capacitor which is connected to ground and the negativeelectrode of the second flying capacitor is connected to the secondoutput node.
 27. The charge pump of claim 23 further comprising acontrol circuit that drives the switching network so that the first,second, and third modes are selected in a repeating sequence.
 28. Thecharge pump of claim 27 wherein the repeating sequence is first mode,second mode, first mode, third mode.
 29. The charge pump of claim 27wherein the repeating sequence is first mode, second mode, third mode.30. A multiple output charge pump comprising: a first flying capacitorhaving a positive electrode and a negative electrode; a second flyingcapacitor having a positive electrode and a negative electrode; a firstoutput node; a second output node; a third output node; and a switchingnetwork configured to provide a first mode where the flying capacitorsare connected in series or in parallel between an input voltage (VIN)and ground, a second mode where the first and second flying capacitorsare connected in series, and a third mode.
 31. The charge pump of claim30 wherein the first mode allows the flying capacitors to be charged toany one of voltages VIN, —VIN, ½ VIN, and −½ VIN.
 32. The charge pump ofclaim 31 wherein for the second mode the negative electrode of thesecond flying capacitor is connected to the input voltage and thepositive electrode of the first flying capacitor is connected to thefirst output node.
 33. The charge pump of claim 32 wherein for the thirdmode the negative electrodes of the flying capacitors are connected tothe input voltage and the positive electrodes of the flying capacitorsare connected to the second output node.
 34. The charge pump of claim 30further comprising a fourth mode where the positive electrode of thefirst flying capacitor is connected to ground and the negativeelectrodes of the first flying capacitor is connected to the thirdoutput node.
 35. The charge pump of claim 30 further comprising a fourthmode where the negative electrodes of the flying capacitors areconnected to ground and the positive electrodes of the flying capacitorsare connected to the third output node.
 36. A charge pump comprising: afirst flying capacitor having a positive electrode and a negativeelectrode; a second flying capacitor having a positive electrode and anegative electrode; a first output node; a second output node; a thirdoutput node; and a switching network configured to provide a first modewhere the flying capacitors are connected in series or in parallelbetween an input voltage (VIN) and ground, a second mode, and a thirdmode.
 37. The charge pump of claim 36 wherein the first mode allows theflying capacitors to be charged to any one of voltages VIN, −VIN, ½ VIN,and −½ VIN.
 38. The charge pump of claim 37 wherein for the second modethe positive electrodes of the flying capacitors are connected to groundand the negative electrodes of the flying capacitors are connected tothe first output node.
 39. The charge pump of claim 38 wherein for thethird mode the first and second flying capacitors are connected inseries with the positive electrode of the second flying capacitor whichis connected to ground and the negative electrode of he first flyingcapacitor is connected to the second output node.
 40. A method foroperating a multiple output charge pump which includes a flyingcapacitor, a first output node, and a second output node, the methodcomprising: configuring a switching network so that the charge pumpoperates in a first mode where a positive electrode of the flyingcapacitor is connected to an input voltage and a negative electrode ofthe flying capacitor is connected to ground; configuring the switchingnetwork so that the charge pump operates in a second mode where thenegative electrode of the flying capacitor is connected to the inputvoltage and the positive electrode of the flying capacitor is connectedto the first output node; and configuring the switching network so thatthe charge pump operates in a third mode where the positive electrode ofthe flying capacitor is connected to ground and the negative electrodeof the flying capacitor is connected to the second output node.
 41. Amethod for operating a multiple output charge pump which includes afirst flying capacitor, a second flying capacitor, a first output node,and a second output node, the method comprising: configuring a switchingnetwork so that the charge pump operates in a first mode where the firstand second flying capacitors are connected in series with a positiveelectrode of the first flying capacitor connected to an input voltageand a negative electrode of the second flying capacitor is connected toground; configuring the switching network so that the charge pumpoperates in a second mode where each negative electrode of the flyingcapacitors is connected to the input voltage and each positive electrodeof the flying capacitors is connected to the first output node; andconfiguring the switching network so that the charge pump operates in athird mode where the positive electrodes of the flying capacitors areconnected to ground and the negative electrodes of the flying capacitorsare connected to the second output node.
 42. A method for operating amultiple output charge pump which includes a first flying capacitor, asecond flying capacitor, a first output node; and a second output node,,the method comprising: configuring a switching network so that thecharge pump operates in a first mode where the first and second flyingcapacitors are connected in series with a positive electrode of thefirst flying capacitor connected to an input voltage and a negativeelectrode of the second flying capacitor is connected to ground;configuring the switching network so that the charge pump operates in asecond mode where positive electrodes of the flying capacitors areconnected to ground and negative electrodes of the flying capacitors areconnected to the first output node; and configuring the switchingnetwork so that the charge pump operates in a third mode where the firstand second flying capacitors are connected in series with the positiveelectrode of the first flying capacitor which is connected to ground andthe negative electrode of the second flying capacitor is connected tothe second output node.
 43. A method for operating a multiple outputcharge pump which includes a first flying capacitor, a second flyingcapacitor, a first output node, a second output node, and a third outputnode, the method comprising: configuring a switching network so that thecharge pump operates in a first mode where the flying capacitors areconnected in series or in parallel between an input voltage (VIN) andground to allow the flying capacitors to be charged to any one ofvoltages VIN, −VIN, ½ VIN, and −½ VIN; configuring the switching networkso that the charge pump operates in a second mode where the first andsecond flying capacitors are connected in series with a negativeelectrode of the second flying capacitor connected to the input voltageand a positive electrode of the first flying capacitor is connected tothe first output node; and configuring the switching network so that thecharge pump operates in a third mode where negative electrodes of theflying capacitors are connected to the input voltage and positiveelectrodes of the flying capacitors are connected to the second outputnode.
 44. The method of claim 43 further comprising configuring theswitching network so that the charge pump operates in a fourth modewhere the positive electrode of the first flying capacitor is connectedto ground and the negative electrodes of the first flying capacitor isconnected to the third output node.
 45. The method of claim 43 furthercomprising configuring the switching network so that the charge pumpoperates in a fourth mode where the negative electrodes of the flyingcapacitors are connected to ground and the positive electrodes of theflying capacitors are connected to the third output node.
 46. A methodfor operating a multiple output charge pump which includes a firstflying capacitor, a second flying capacitor, a first output node, asecond output node, and a third output node, the method comprising:configuring a switching network so that the charge pump operates in afirst mode where the flying capacitors are connected in series or inparallel between an input voltage (VIN) and ground to allow the flyingcapacitors to be charged to any one of voltages VIN, —VIN, ½ VIN, and −½VIN; configuring the switching network so that the charge pump operatesin a second mode where the positive electrodes of the flying capacitorsare connected to ground and the negative electrodes of the flyingcapacitors are connected to the first output node; and configuring theswitching network so that the charge pump operates in a third mode wherethe first and second flying capacitors are connected in series with thepositive electrode of the second flying capacitor which is connected toground and the negative electrode of the first flying capacitor isconnected to the second output node.